ad844sq-883b Analog Devices, Inc., ad844sq-883b Datasheet - Page 8

• Manufacturer Part Number: ad844sq-883b
• Description: 60 Mhz, 2000 V/us Monolithic Op Amp
• Manufacturer: Analog Devices, Inc.

AD844
UNDERSTANDING THE AD844
The AD844 can be used in ways similar to a conventional op
amp while providing performance advantages in wideband
applications. However, there are important differences in the
internal structure that need to be understood in order to
optimize the performance of the AD844 op amp.
Open-Loop Behavior
Figure 1 shows a current feedback amplifier reduced to essen-
tials. Sources of fixed dc errors, such as the inverting node bias
current and the offset voltage, are excluded from this model
and are discussed later. The most important parameter limiting
the dc gain is the transresistance, R
finite value of R
gain in a conventional op amp.
The current applied to the inverting input node is replicated by
the current conveyor so as to flow in resistor R
developed across R
Voltage gain is the ratio R
and R
loop current gain is another measure of gain and is determined
by the beta product of the transistors in the voltage follower
stage (see Figure 4); it is typically 40,000.
The important parameters defining ac behavior are the trans-
capacitance, C
The time constant formed by these components is analogous to
the dominant pole of a conventional op amp and thus cannot
be reduced below a critical value if the closed-loop system is to
be stable. In practice, C
(typically 4.5 pF) so that the feedback resistor can be maximized
while maintaining a fast response. The finite R
closed-loop response in some applications as will be shown.
The open-loop ac gain is also best understood in terms of the
transimpedance rather than as an open-loop voltage gain. The
open-loop pole is formed by R
typically 4.5 pF, the open-loop corner frequency occurs at
about 12 kHz. However, this parameter is of little value in
determining the closed-loop response.
IN
= 50 Ω, the voltage gain is about 60,000. The open-
+1
R
IN
I
IN
t
Figure 1. Equivalent Schematic
, and the external feedback resistor (not shown).
t
is analogous to the finite open-loop voltage
t
is buffered by the unity gain voltage follower.
I
IN
t
t
/R
is held to as low a value as possible
IN
. With typical values of R
t
in parallel with C
R
t
t
, which is ideally infinite. A
C
t
IN
also affects the
t
t
. The voltage
. Since C
+1
t
= 3 MΩ
t
is
–8–
Response as an Inverting Amplifier
Figure 2 shows the connections for an inverting amplifier.
Unlike a conventional amplifier, the transient response and the
small signal bandwidth are determined primarily by the value of
the external feedback resistor, R1, rather than by the ratio of
R1/R2 as is customarily the case in an op amp application. This
is a direct result of the low impedance at the inverting input. As
with conventional op amps, the closed-loop gain is –R1/R2.
The closed-loop transresistance is simply the parallel sum of R1
and R
and R
only 0.02% to 0.07% lower than R1. This small error will often
be less than the resistor tolerance.
When R1 is fairly large (above 5 kΩ) but still much less than R
the closed-loop HF response is dominated by the time constant
R1C
will provide only a fraction of its bandwidth potential. Because
of the absence of slew rate limitations under these conditions,
the circuit will exhibit a simple single pole response even under
large signal conditions.
In Figure 2, R3 is used to properly terminate the input if desired.
R3 in parallel with R2 gives the terminated resistance. As R1
is lowered, the signal bandwidth increases but the time
constant R1C
in the closed-loop response. Therefore, the closed-loop
response becomes complex, and the pulse response shows
overshoot. When R2 is much larger than the input resistance,
R
to this input, but as R2 becomes comparable to R
feedback is absorbed at Pin 2, resulting in a more heavily
damped response. Consequently, for low values of R2 it is
possible to lower R1 without causing instability in the
closed-loop response. Table I lists combinations of R1 and
R2 and the resulting frequency response for the circuit of
Figure 2. TPC 13 shows the very clean and fast ± 10 V pulse
response of the AD844.
IN
, at Pin 2, most of the feedback current in R1 is delivered
t
. Under such conditions the AD844 is over-damped and
t
t
. Since R1 will generally be in the range 500 Ω to 2 kΩ
is about 3 MΩ the closed-loop transresistance will be
OPTIONAL
V
IN
R3
t
becomes comparable to higher order poles
Figure 2. Inverting Amplifier
R2
AD844
R1
R
L
IN
C
, less of the
V
OUT
L
REV. E
t
,