MF10ACWM National Semiconductor, MF10ACWM Datasheet - Page 20
MF10ACWM
Manufacturer Part Number
MF10ACWM
Description
Manufacturer
National Semiconductor
Datasheet
1.MF10ACWM.pdf
(28 pages)
Specifications of MF10ACWM
Architecture
Switched Capacitor
Filter Type
Universal
Cutoff Frequency
30KHz
Dual Supply Voltage (typ)
±5V
Power Supply Requirement
Single/Dual
Operating Temperature (min)
0C
Operating Temperature (max)
70C
Operating Temperature Classification
Commercial
Package Type
SOIC W
Lead Free Status / Rohs Status
Not Compliant
www.national.com
3.0 Applications Information
The MF10 is a general-purpose dual second-order state
variable filter whose center frequency is proportional to the
frequency of the square wave applied to the clock input
(f
the filter center frequency f
f
varied over a wide frequency range by adjusting the clock
frequency. If desired, the f
external resistors as in Figures 9, 10, 11, 13, 14, 15 . The
filter Q and gain are determined by external resistors.
All of the five second-order filter types can be built using
either section of the MF10. These are illustrated in Figure 1
through Figure 5 along with their transfer functions and some
related equations. Figure 6 shows the effect of Q on the
shapes of these curves. When filter orders greater than two
are desired, two or more MF10 sections can be cascaded.
3.1 DESIGN EXAMPLE
In order to design a second-order filter section using the
MF10, we must define the necessary values of three param-
eters: f
band gain; and the filter’s Q. These are determined by the
characteristics required of the filter being designed.
As an example, let’s assume that a system requires a
fourth-order Chebyshev low-pass filter with 1 dB ripple, unity
gain at DC, and 1000 Hz cutoff frequency. As the system
order is four, it is realizable using both second-order sections
of an MF10. Many filter design texts include tables that list
the characteristics (f
filter sections needed to synthesize a given higher-order
filter. For the Chebyshev filter defined above, such a table
yields the following characteristics:
f
f
For unity gain at DC, we also specify:
H
H
The desired clock-to-cutoff-frequency ratio for the overall
filter of this example is 100 and a 100 kHz clock signal is
available. Note that the required center frequencies for the
two second-order sections will not be obtainable with
clock-to-center-frequency ratios of 50 or 100. It will be nec-
essary to adjust
±
CLK
0A
0B
CLK
6%) by using a crystal clock oscillator, or can be easily
0A
0B
= 529 Hz Q
= 993 Hz Q
/100 or f
= 1
= 1
). By connecting pin 12 to the appropriate DC voltage,
0
, the filter section’s center frequency; H
CLK
A
B
/50. f
= 0.785
= 3.559
O
O
and Q) of each of the second-order
can be very accurately set (within
O
CLK
can be made equal to either
/f
O
ratio can be altered by
0
, the pass-
20
externally. From Table 1 , we see that Mode 3 can be used to
produce a low-pass filter with resistor-adjustable center fre-
quency.
In most filter designs involving multiple second-order stages,
it is best to place the stages with lower Q values ahead of
stages with higher Q, especially when the higher Q is greater
than 0.707. This is due to the higher relative gain at the
center frequency of a higher-Q stage. Placing a stage with
lower Q ahead of a higher-Q stage will provide some attenu-
ation at the center frequency and thus help avoid clipping of
signals near this frequency. For this example, stage A has
the lower Q (0.785) so it will be placed ahead of the other
stage.
For the first section, we begin the design by choosing a
convenient value for the input resistance: R
absolute value of the passband gain H
1 by choosing R
If the 50/100/CL pin is connected to mid-supply for nominal
100:1 clock-to-center-frequency ratio, we find R
The resistors for the second section are found in a similar
fashion:
The complete circuit is shown in Figure 16 for split
power supplies. Supply bypass capacitors are highly
recommended.
4A
such that: R
4A
= −H
OLPA
OLPA
R
is made equal to
1A
1A
= R
2A
= 20k. The
1A
by:
= 20k.
±
5V