MAX1711 Maxim, MAX1711 Datasheet - Page 13

• Manufacturer Part Number: MAX1711
• Description: High-Speed / Digitally Adjusted Step-Down Controllers for Notebook CPUs
• Manufacturer: Maxim

side MOSFET, which causes a faster inductor-current
discharge ramp. The on-times guaranteed in the
Electrical Characteristics are influenced by switching
delays in the external high-side power MOSFET. The
exact switching frequency will depend on gate charge,
internal gate resistance, source inductance, and DH out-
put drive characteristics.
Two external factors that can influence switching-fre-
quency accuracy are resistive drops in the two conduc-
tion loops (including inductor and PC board resistance)
and the dead-time effect. These effects are the largest
contributors to the change of frequency with changing
load current. The dead-time effect is a notable disconti-
nuity in the switching frequency as the load current is
varied (see Typical Operating Characteristics ). It occurs
whenever the inductor current reverses, most commonly
at light loads with SKIP high. With reversed inductor cur-
rent, the inductor’s EMF causes LX to go high earlier
than normal, extending the on-time by a period equal to
the low-to-high dead time. For loads above the critical
conduction point, the actual switching frequency is:
where V
in the inductor discharge path, including synchronous
rectifier, inductor, and PC board resistances; V
the sum of the resistances in the charging path, and t
is the on-time calculated by the MAX1710/MAX1711.
There are three integrator amplifiers that provide a fine
adjustment to the output regulation point. One amplifier
monitors the difference between GNDS and GND, while
another monitors the difference between FBS and FB.
The third amplifier integrates the difference between REF
and the DAC output. These three transconductance
amplifiers’ outputs are directly summed inside the chip,
so the integration time constant can be set easily with a
capacitor. The g
The integrator block has an ability to move and correct
the output voltage by about -2%, +4%. For each amplifi-
er, the differential input voltage range is about ±50mV
total, including DC offset and AC ripple. The voltage
gain of each integrator is about 80V/V.
The FBS amplifier corrects for DC voltage drops in PC
board traces and connectors in the output bus path
between the DC-DC converter and the load. The GNDS
amplifier performs a similar DC correction task for the
output ground bus. The third amplifier provides an aver-
aging function that forces V
DROP1
Step-Down Controllers for Notebook CPUs
f
is the sum of the parasitic voltage drops
m
______________________________________________________________________________________
of each amplifier is 160µmho (typical).
t
ON IN
V
OUT
(
Integrator Amplifiers (CC)
V
V
OUT
V
DROP
DROP
to be regulated at the
1
2
)
High-Speed, Digitally Adjusted
DROP2
ON
is
average value of the output ripple waveform. If the inte-
grator amplifiers are disabled, V
valleys of the output ripple waveform. This creates a
slight load-regulation characteristic in which the output
voltage rises approximately 1% (up to 1/2 the peak
amplitude of the ripple waveform as a limit) when under
light loads.
Integrators have both beneficial and detrimental charac-
teristics. While they do correct for drops due to DC bus
resistance and tighten the DC output voltage tolerance
limits by averaging the peak-to-peak output
ripple, they can interfere with achieving the fastest possi-
ble load-transient response. The fastest transient
response is achieved when all three integrators are dis-
abled. This works very well when the MAX1710/
MAX1711 circuit can be placed very close to the CPU.
There is often a connector, or at least many milliohms of
PC board trace resistance, between the DC-DC convert-
er and the CPU. In these cases, the best strategy is to
place most of the bulk bypass capacitors close to the
CPU, with just one capacitor on the other side of the
connector near the MAX1710/MAX1711 to control ripple
if the CPU card is unplugged. In this situation, the
remote-sense lines and integrators provide a real benefit.
When both GNDS and FBS are tied to V
three integrators are disabled, CC can be left uncon-
nected, which eliminates a component.
At light loads, an inherent automatic switchover to PFM
takes place. This switchover is effected by a comparator
that truncates the low-side switch on-time at the inductor
current’s zero crossing. This mechanism causes the
threshold between pulse-skipping PFM and non-skip-
ping PWM operation to coincide with the boundary
between continuous and discontinuous inductor-current
operation (also known as the “critical conduction” point;
see Continuous to Discontinuous Inductor Current Point
vs. Input Voltage graphs in the Typical Operating
Characteristics ). For a battery range of 7V to 24V this
threshold is relatively constant, with only a minor depen-
dence on battery voltage.
where K is the On-Time Scale factor (see Table 5). The
load-current level at which PFM/PWM crossover occurs,
I
rent, which is a function of the inductor value (Figure 3).
For example, in the standard application circuit with t
= 300ns at 24V, V
pulse-skipping operation occurs at I
LOAD(SKIP)
Automatic Pulse-Skipping Switchover
, is equal to 1/2 the peak-to-peak ripple cur-
I
LOAD SKIP
OUT
= 2V, and L = 2µH, switchover to
(
)
2
K
L
OUT
is regulated at the
LOAD
CC
= 1.65A or
so that all
ON
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