ISL6327 Intersil Corporation, ISL6327 Datasheet - Page 25

• Manufacturer Part Number: ISL6327
• Description: Enhanced 6-Phase PWM Controller
• Manufacturer: Intersil Corporation

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be used, higher per-phase currents are possible. In cases
where board space is the limiting constraint, current can be
pushed as high as 40A per phase, but these designs require
heat sinks and forced air to cool the MOSFETs, inductors,
and heat-dissipating surfaces.
MOSFETS
The choice of MOSFETs depends on the current each
MOSFET will be required to conduct; the switching
frequency; the capability of the MOSFETs to dissipate heat;
and the availability and nature of heat sinking and air flow.
LOWER MOSFET POWER CALCULATION
The calculation for heat dissipated in the lower MOSFET is
simple, since virtually all of the heat loss in the lower
MOSFET is due to current conducted through the channel
resistance (R
continuous output current; I
current (see Equation 1); d is the duty cycle (V
L is the per-channel inductance.
An additional term can be added to the lower-MOSFET loss
equation to account for additional loss accrued during the
dead time when inductor current is flowing through the
lower-MOSFET body diode. This term is dependent on the
diode forward voltage at I
frequency, f
the beginning and the end of the lower-MOSFET conduction
interval respectively.
Thus the total maximum power dissipated in each lower
MOSFET is approximated by the summation of P
P
UPPER MOSFET POWER CALCULATION
In addition to R
MOSFET losses are due to currents conducted across the
input voltage (V
higher portion of the upper-MOSFET losses are dependent
on switching frequency, the power calculation is more
complex. Upper MOSFET losses can be divided into
separate components involving the upper-MOSFET
switching times; the lower-MOSFET body-diode reverse-
recovery charge, Q
conduction loss.
When the upper MOSFET turns off, the lower MOSFET does
not conduct any portion of the inductor current until the
voltage at the phase node falls below ground. Once the
lower MOSFET begins conducting, the current in the upper
MOSFET falls to zero as the current in the lower MOSFET
ramps up to assume the full inductor current. In Equation 26,
P
P
LOW,2
LOW 1
LOW 2
,
,
.
=
=
r
V
S
DS ON
D ON
; and the length of dead times, t
DS(ON)
(
(
DS(ON)
IN
)
) during switching. Since a substantially
)
f
S
rr
⎛
⎜
⎝
). In Equation 24, I
; and the upper MOSFET R
I
----- -
N
M
⎛
⎝
I
----- -
⎞
⎟
⎠
N
M
losses, a large portion of the upper-
2
(
+
M
1 d
I
-------- -
, V
PP
–
PP
2
25
D(ON)
⎞ t
⎠
)
is the peak-to-peak inductor
+
d1
I
--------------------------------
L PP
,
+
2
; the switching
⎛
⎜
⎝
12
I
----- -
(
N
M
M
1 d
–
–
is the maximum
I
-------- -
PP
2
)
d1
⎞
⎟
⎠
OUT
t
d2
and t
DS(ON)
LOW,1
/V
IN
d2
(EQ. 24)
(EQ. 25)
); and
, at
and
ISL6327
the required time for this commutation is t
approximated associated power loss is P
At turn on, the upper MOSFET begins to conduct and this
transition occurs over a time t
approximate power loss is P
A third component involves the lower MOSFET’s reverse-
recovery charge, Q
commutated to the upper MOSFET before the lower-
MOSFET’s body diode can draw all of Q
through the upper MOSFET across VIN. The power
dissipated as a result is P
Finally, the resistive part of the upper MOSFET’s is given in
Equation 29 as P
The total power dissipated by the upper MOSFET at full load
can now be approximated as the summation of the results
from Equations 26, 27, 28 and 29. Since the power
equations depend on MOSFET parameters, choosing the
correct MOSFETs can be an iterative process involving
repetitive solutions to the loss equations for different
MOSFETs and different switching frequencies.
Current Sensing Resistor
The resistors connected to the Isen+ pins determine the
gains in the load-line regulation loop and the channel-current
balance loop as well as setting the overcurrent trip point.
Select values for these resistors by the Equation 30.
where R
pin, N is the active channel number, R
the current sense element, either the DCR of the inductor or
R
desired overcurrent trip point. Typically, I
to be 1.3 times the maximum load current of the specific
application.
With integrated temperature compensation, the sensed
current signal is independent on the operational temperature
of the power stage, i.e. the temperature effect on the current
sense element R
temperature compensation function. R
P
P
P
P
R
UP 1 ,
UP 2 ,
UP 3 ,
UP 4 ,
SENSE
ISEN
≈
≈
≈
=
=
V
r
V
DS ON
ISEN
V
IN
depending on the sensing method, and I
IN
---------------------- -
85 10
IN
(
⎛
⎝
⎛
⎝
R
×
I
----- -
I
----- -
Q
N
N
M
M
X
is the sense resistor connected to the ISEN+
rr
)
+
–
–
f
S
⎛
⎜
⎝
6
I
-------- -
I
-------- -
X
UP,4
PP
PP
I
----- -
2
N
2
M
I
------------- -
OCP
is cancelled by the integrated
rr
⎞
⎟
⎠
⎞ t
⎠
⎞ t
⎠
N
. Since the inductor current has fully
2
⎛
⎜
⎝
⎛
⎜
⎝
.
d
----
----
2
2
2
1
+
⎞
⎟
⎠
⎞
⎟
⎠
I
--------- - d
f
f
UP,3
PP
12
S
S
2
UP,2
2
and is approximately
. In Equation 27, the
.
X
X
is the resistance of
rr
OCP
in Equation 30
UP,1
1
, it is conducted
and the
.
can be chosen
OCP
June 5, 2006
(EQ. 29)
(EQ. 26)
(EQ. 27)
(EQ. 28)
(EQ. 30)
FN9276.1
is the