ISL6310 INTERSIL [Intersil Corporation], ISL6310 Datasheet - Page 21

• Manufacturer Part Number: ISL6310
• Description: Two-Phase Buck PWM Controller with High Current Integrated MOSFET Drivers
• Manufacturer: INTERSIL [Intersil Corporation]

yields a solution that is always stable with very close to ideal
transient performance.
The feedback resistor, R
outlined in See “Load-Line (Droop) Regulation” on page 12.
Select a target bandwidth for the compensated system, F
The target bandwidth must be large enough to assure
adequate transient performance, but smaller than 1/3 of the
per-channel switching frequency. The values of the
compensation components depend on the relationships of f
to the L-C pole frequency and the ESR zero frequency. For
each of the following three, there is a separate set of
equations for the compensation components.
Case 3:
In Equations 28, L is the per-channel filter inductance
divided by the number of active channels; C is the sum total
of all output capacitors; ESR is the equivalent series
resistance of the bulk output filter capacitance; and V
the peak-to-peak sawtooth signal amplitude as described in
the Electrical Specifications on page 5.
Once selected, the compensation values in Equations 28
assure a stable converter with reasonable transient
performance. In most cases, transient performance can be
improved by making adjustments to R
value of R
oscilloscope until no further improvement is noted. Normally,
C
Equations 28 unless some performance issue is noted.
Case 2:
Case 1:
1
will not need adjustment. Keep the value of C
2
while observing the transient performance on an
---------------------------
2π
R
C
---------------------------
2π
R
C
2
1
2
1
⋅
F
R
C
=
=
0
⋅
1
2
2
=
=
L C
1
>
R
------------------------------------------------------------------------------- -
(
=
=
L C
2π
⋅
R
------------------------------------------------ -
2π V
1
-------------------------------- -
2π C ESR
⋅
1
R
-------------------------------------------------------------- -
2π V
⋅
)
0.66 V
V
--------------------------------------------------------------- -
2
⋅
≤
⋅
1
⋅
1
0.66 V
2π F
----------------------------------------------------------- -
>
OSC
⋅
⋅
F
, has already been chosen as
⋅
F
OSC
1
0
F
2π F
-----------------------------------------------
⋅
2
0
0.66 V
⋅
OSC
⋅
0
<
0.66 V
21
⋅
⋅
⋅
-------------------------------- -
2π C ESR
⋅
0.66 V
V
0
IN
0.66 V
(
⋅
2π
OSC
⋅
IN
R
⋅
0
⋅
V
⋅
⋅
⋅
1
R
⋅
ESR
)
OSC
⋅
IN
2
⋅
V
1
⋅
1
IN
f
⋅
⋅
⋅
OSC
⋅
0
IN
⋅
R
F
F
IN
ESR
2
2
0
1
⋅
⋅
0
. Slowly increase the
⋅
⋅
⋅
⋅
L C
L C
C
L
L C
⋅
L
⋅
⋅
1
from
(EQ. 28)
OSC
0
is
.
0
ISL6310
The optional capacitor C
noise away from the PWM comparator (see Figure 20). Keep
a position available for C
frequency capacitor of between 22pF and 150pF in case any
leading edge jitter problem is noted.
Compensating the Converter operating without
Load-Line Regulation
The ISL6310 multi-phase converter operating without load
line regulation behaves in a similar manner to a voltage-
mode controller. This section highlights the design
consideration for a voltage-mode controller requiring external
compensation. To address a broad range of applications, a
type-3 feedback network is recommended (see Figure 21).
Figure 22 highlights the voltage-mode control loop for a
synchronous-rectified buck converter, applicable, with a
small number of adjustments, to the multi-phase ISL6310
circuit. The output voltage (V
reference voltage, VREF, level. The error amplifier output
(COMP pin voltage) is compared with the oscillator (OSC)
modified saw-tooth wave to provide a pulse-width modulated
wave with an amplitude of V
PWM wave is smoothed by the output filter (L and C). The
output filter capacitor bank’s equivalent series resistance is
represented by the series resistor ESR.
The modulator transfer function is the small-signal transfer
function of V
DC gain, given by d
output filter, with a double pole break frequency at F
zero at F
represent the individual channel inductance and its DCR
divided by 2 (equivalent parallel value of the two output
inductors), while C and ESR represents the total output
capacitance and its equivalent series resistance.
F
LC
FIGURE 21. COMPENSATION CONFIGURATION FOR
=
---------------------------
2π
C
R
CE
3
⋅
3
1
. For the purpose of this analysis, L and DCR
L C
OUT
⋅
NON-LOAD-LINE REGULATED ISL6310 CIRCUIT
/V
COMP
MAX
R
R
1
2
V
2
F
2
. This function is dominated by a
, is sometimes needed to bypass
IN
C
, and be prepared to install a high
CE
2
/V
IN
C
OUT
=
OSC
1
at the PHASE node. The
-------------------------------- -
2π C ESR
) is regulated to the
, and shaped by the
⋅
COMP
VDIFF
1
FB
⋅
ISL6310
December 12, 2006
LC
FN9209.3
and a