IR3637STRPBF International Rectifier, IR3637STRPBF Datasheet - Page 8

• Manufacturer Part Number: IR3637STRPBF
• Description: IC SYNC BUCK REGULATOR 8 SOIC
• Manufacturer: International Rectifier

Specifications of IR3637STRPBF

• Pwm Type: Voltage Mode
• Number Of Outputs: 1
• Frequency - Max: 440kHz
• Duty Cycle: 85%
• Voltage - Supply: 4.5 V ~ 14 V
• Buck: Yes
• Boost: No
• Flyback: No
• Inverting: No
• Doubler: No
• Divider: No
• Cuk: No
• Isolated: No
• Operating Temperature: 0°C ~ 125°C
• Package / Case: 8-SOIC (3.9mm Width)
• Frequency-max: 440kHz
• Output Current: 15A
• Frequency: 400kHz
• Supply Voltage Range: 4.5V To 5.5V
• Digital Ic Case Style: SOIC
• No. Of Pins: 8
• Operating Temperature Range: 0°C To +125°C
• Termination Type: SMD
• Rohs Compliant: Yes
• Filter Terminals: SMD
• Controller Type: PWM
• For Use With: IRPP3637-12A - KIT REF DES 12A 1PH SYNC BUCKIRDC3637 - BOARD EVAL SYNC BUCK REGULATOR
• Lead Free Status / RoHS Status: Lead free / RoHS Compliant
• Other names: IR3637STRPBF; IR3637STRPBFTR

IR3637SPBF
For this design, IRF8910 is a good choice. The device
provides two N-MOSFETs in a compact SOIC 8-Pin pack-
age.
The IRF8910 has the following data:
The total conduction losses will be:
The switching loss is more difficult to calculate, even
though the switching transition is well understood. The
reason is the effect of the parasitic components and
switching times during the switching procedures such
as turn-on / turnoff delays and rise and fall times. The
control MOSFET contributes to the majority of the switch-
ing losses in synchronous Buck converter. The synchro-
nous MOSFET turns on under zero voltage conditions,
therefore, the turn on losses for synchronous MOSFET
can be neglected. With a linear approximation, the total
switching loss can be expressed as:
The switching time waveform is shown in figure 7.
From IRF8910 data sheet:
8
P
Where:
V
t
t
T = Switching Period
I
LOAD
r
f
SW
DS(OFF)
= Rise Time
= Fall Time
V
I
R
R
P
ϑ = 1.4 according to the IRF8910 data sheet for
150 C junction temperature
P
D
90%
10%
=
DSS
CON(TOTAL)
CON(TOTAL)
DS(onh)
DS(on)
V
V
= 10A
= Load Current
GS
V
DS
Figure 7 - Switching time waveforms.
= 20V
DS(OFF)
= Drain to Source Voltage at off time
t
d
=13.4Ω @ V
2
(ON)
=18.3Ω @ V
=P
=0.83W
CON
×
(Upper Switch)+P
t
r
+
T
t
GS
t
r
GS
f
=10V (Upper FET)
×
=4.5V (Lower FET)
t
d
I
(OFF)
LOAD
t
t
r
f
= 4.1ns
= 10ns
CON
---(6)
(Lower Switch)
t
f
www.irf.com
These values are taken under a certain condition test.
For more detail please refer to the IRF8910 data sheet.
By using equation (6), we can calculate the switching
losses.
Feedback Compensation
The IR3637 is a voltage mode controller; the control loop
is a single voltage feedback path including error ampli-
fier and error comparator. To achieve fast transient re-
sponse and accurate output regulation, a compensation
circuit is necessary. The goal of the compensation net-
work is to provide a closed loop transfer function with the
highest 0dB crossing frequency and adequate phase
margin (greater than 45 ).
The output LC filter introduces a double pole, –40dB/
decade gain slope above its corner resonant frequency,
and a total phase lag of 180 (see Figure 8). The Reso-
nant frequency of the LC filter expressed as follows:
Figure 8 shows gain and phase of the LC filter. Since we
already have 180 phase shift just from the output filter,
the system risks being unstable.
The IIR3637’s error amplifier is a differential-input transcon-
ductance amplifier. The output is available for DC gain
control or AC phase compensation.
The E/A can be compensated with or without the use of
local feedback. When operated without local feedback
the transconductance properties of the E/A become evi-
dent and can be used to cancel one of the output filter
poles. This will be accomplished with a series RC circuit
from Comp pin to ground as shown in Figure 9.
0dB
Gain
P
F
LC
SW
=
= 95mW
Figure 8 - Gain and phase of LC filter.
2π×
F
LC
Frequency
-40dB/decade
1
L
O
×C
O
-180
0
Phase
---(7)
F
LC
Frequency
06/16/05
Rev.1.1