ISL6310EVAL1Z Intersil, ISL6310EVAL1Z Datasheet - Page 24

• Manufacturer Part Number: ISL6310EVAL1Z
• Description: EVALUATION BOARD FOR ISL6310
• Manufacturer: Intersil

Specifications of ISL6310EVAL1Z

• Main Purpose: DC/DC, Step Down
• Outputs And Type: 1, Non-Isolated
• Voltage - Output: 1.5V
• Current - Output: 60A
• Voltage - Input: 5 ~ 12V
• Regulator Topology: Buck
• Frequency - Switching: 400kHz
• Board Type: Fully Populated
• Utilized Ic / Part: ISL6310
• Lead Free Status / RoHS Status: Lead free / RoHS Compliant
• Power - Output: -

Switching Frequency
There are a number of variables to consider when choosing
the switching frequency, as there are considerable effects on
the upper MOSFET loss calculation. These effects are
outlined in “MOSFETs” on page 17, and they establish the
upper limit for the switching frequency. The lower limit is
established by the requirement for fast transient response
and small output-voltage ripple as outlined in “Output Filter
Design” on page 23. Choose the lowest switching frequency
that allows the regulator to meet the transient-response
requirements.
Switching frequency is determined by the selection of the
frequency-setting resistor, R
are provided to assist in selecting the correct value for R
R
Input Capacitor Selection
The input capacitors are responsible for sourcing the AC
component of the input current flowing into the upper
MOSFETs. Their RMS current capacity must be sufficient to
handle the ac component of the current drawn by the upper
MOSFETs which is related to duty cycle and the number of
active phases.
For a two-phase design, use Figure 25 to determine the
input-capacitor RMS current requirement set by the duty
cycle, maximum sustained output current (I
of the peak-to-peak inductor current (I
bulk capacitor with a ripple current rating which will minimize
the total number of input capacitors required to support the
RMS current calculated. The voltage rating of the capacitors
should also be at least 1.25 times greater than the maximum
input voltage. Figure 26 provides the same input RMS
current information for single-phase designs. Use the same
approach for selecting the bulk capacitor type and number.
Low ESL, high-frequency ceramic capacitors are needed in
addition to the input bulk capacitors to suppress leading and
FS
200
100
=
50
20
10
10
FIGURE 24. R
[
10.61 1.035
100k
–
SWITCHING FREQUENCY (Hz)
200k
⋅
FS
log
(
vs SWITCHING FREQUENCY
F SW
FS
24
)
]
. Figure 24 and Equation 43
500k
L,PP
1M
) to I
O
), and the ratio
O
. Select a
2M
(EQ. 43)
FS
.
ISL6310
falling edge voltage spikes. The spikes result from the high
current slew rate produced by the upper MOSFET turn on and
off. Place them as close as possible to each upper MOSFET
drain to minimize board parasitics and maximize suppression.
Layout Considerations
MOSFETs switch very fast and efficiently. The speed with
which the current transitions from one device to another
causes voltage spikes across the interconnecting
impedances and parasitic circuit elements. These voltage
spikes can degrade efficiency, radiate noise into the circuit
and lead to device overvoltage stress. Careful component
layout and printed circuit design minimizes the voltage
spikes in the converter. Consider, as an example, the turnoff
transition of the upper PWM MOSFET. Prior to turnoff, the
upper MOSFET was carrying channel current. During the
turnoff, current stops flowing in the upper MOSFET and is
picked up by the lower MOSFET. Any inductance in the
switched current path generates a large voltage spike during
the switching interval. Careful component selection, tight
FIGURE 26. NORMALIZED INPUT-CAPACITOR RMS
FIGURE 25. NORMALIZED INPUT-CAPACITOR RMS
0.3
0.2
0.1
0.6
0.4
0.2
0
0
0
0
I
I
I
L,PP
L,PP
L,PP
CURRENT FOR SINGLE-PHASE CONVERTER
= 0
= 0.5 I
= 0.75 I
CURRENT FOR 2-PHASE CONVERTER
I
I
I
L,PP
L,PP
L,PP
0.2
0.2
= 0
= 0.5 I
= 0.75 I
O
O
O
DUTY CYCLE (V
DUTY CYCLE (V
O
0.4
0.4
0.6
0.6
IN/
IN
/V
V
O
O
)
)
0.8
0.8
August 7, 2008
FN9209.4
1.0
1.0